View TS1102-25EG5T_4863833.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

ts1102 page 1 ? 2011 touchstone semiconductor, inc. all rights reserved. features ? improved electrical p erformance over the max9938 and the max9634 ? ultra - low supply urrent: 1a ? wide input common mode range: +2v to +25v ? low input offset voltage: 2 0 0 (max) ? low gain error: 0. 5 % (max) ? voltage output ? four gain options available: ts1102 - 25 : gain = 25v/v ts1102 - 50 : gain = 50v/v ts1102 - 100 : gain = 100v/v ts1102 - 200 : gain = 200v/v ? 5 - pin sot23 packaging applications notebook computers current - shunt measurement power management systems battery monitoring motor control load protection smart battery packs/chargers description the voltage - output ts1102 current - sense amplifiers are form - factor identical and electrical improvements to the max9938 and the max9634 current - sense amplifiers. the ts1102 is the latest addition to the ts1100 family of current - sense amplifiers. onsuming a very low 1a supply current, the ts1102 high - side current - se nse amplifiers combine a 2 0 0 - v (max) v os and a 0. 5 % (max) gain error for cost - sensitive applications . for all high - side current - sensing applications, the ts1102 features a wide input common - mode voltage range from 2 v to 2 5 v. the sot23 package make s the ts1102 an ideal choice for pcb - area - critical, low - current, high - accuracy current - sense app lications in all battery - powered, remote or hand - held portable instruments. all ts1102 s are specified for operation over the - 40c to +105 c extended temperature range. a 1a, 200 v os sot23 precision current - sense amplifier typical application circuit part gain option ts1102 - 25 25 v/v ts1102 - 50 50 v/v ts1102 - 100 100 v/v ts1102 - 200 2 00 v/v t he touchstone semicondu c tor logo is a registered trademark of touchstone semiconductor, incorporated. percent of units - % input offset voltage - v 0 10 25 35 10 30 0 40 15 20 input offset voltage histogram 5 20 30 50
ts1102 page 2 ts1102 ds r1p0 rtfds absolute maximum rat ings rs+, rs - to gnd ................................ .............. - 0.3v to + 27 v out to gnd ................................ ........................ - 0.3v to +6v rs+ to rs - ................................ ................................ ..... 27 v short - circuit duration: out to gnd .................... continuous continuous input current (any pin) ............................ 20ma continuous power dissipation (t a = +70c) 5 - pin sot23 (derate at 3.9mw/c above +70c) .. 312mw operating temperature range .................... - 40c to +105 c junction temperature ................................ ................ +150c storage temperature range ....................... - 65c to +150c lead temperature (soldering, 10s) ........................... +300c soldering temperature (reflow) ............................ +260c electrical and thermal s tresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. these are stress ratings only and functional operation of the device at these or any other condition beyond those indicated in the operational sections of the specifications is not implied. exposure to any absolute maximum rating conditions for extended periods may affect device reliability and lifetime . package/ordering inf ormation order number part marking carrier quantity ts1102 - 25eg5tp tad s tape & reel ----- ts1102 - 25eg5t tape & reel 3000 ts1102 - 50eg5tp tad t tape & reel ----- ts1102 - 50eg5t tape & reel 3000 ts1102 - 100eg5tp tad u tape & reel ----- ts1102 - 100eg5t tape & reel 3000 ts1102 - 200eg5tp tad v tape & reel ----- ts1102 - 200eg5t tape & reel 3000 lead - free program: touchstone semico nductor supplies only lead - free packaging. consult touchstone semiconductor for products specified with wider operating temperature ranges.
ts1102 ts1102 ds r1p0 page 3 rtfds electrical character istics v rs+ = v rs - = 3.6v; v sense = (v rs+ - v rs - ) = 0v; c out = 47nf; t a = - 40c to +105 c, unless otherwise noted. typical values are at t a = +25c. see note 1 parameter symbol conditions min typ max units supply current (note 2) i cc t a = +25c 0.68 0.85 a 1. 0 v rs+ = 2 5 v t a = +25c 1.0 1.2 common - mode input range v cm guaranteed by cmrr 2 2 5 v common - mode rejection ratio cmrr 2 v < v rs+ < 2 5 v 120 150 db input offset voltage (note 3) v os t a = +25c 30 2 0 0 3 00 gain g ts1102 - 25 25 v/v ts1102 - 50 50 ts1102 - 100 100 ts1102 - 200 200 gain error (note 4) ge t a = +25c 0.1 0. 5 % 0.6 output resistance (note 5) r out ts1102 - 25/50/100 7.0 10 13.2 k ts1102 - 200 14.0 20 26.4 out low voltage v ol gain = 25 5 mv gain = 50 10 gain = 100 2 0 gain = 200 4 0 out high voltage (note 6) v oh v oh = v rs - - v out 0. 05 0.2 v output settling time t s ts1102 - 25/50/100 1% final value, v out = 3 v 2.2 m s ts1102 - 200 4.3 m s note 1: all devices are 100% production tested at t a = +25c. all temperature limits are guaranteed by product characterization. note 2: extrapolated to v out = 0. i cc is the total current into the rs+ and the rs - pins. note 3: input offset voltage v os is extrapolated from v out with v sense set to 1mv . note 4: gain error is calculated by applying two values for v sense and then calculating the error of the actual slope vs. the ideal transfer characteristic: for gain = 25, the applied v sense is 20mv and 120mv. for g ain = 50, the applied v sense is 10mv and 60mv. for g ain = 100, the applied v sense is 5mv and 30mv. for g ain = 200, the applied v sense is 2.5mv and 15mv. note 5: the device is stable for any capacitive load at v out . note 6: v oh is the voltage from v rs - to v out with v sense = 3.6v/gain.
ts1102 page 4 ts1102 ds r1p0 rtfds supply current vs common - mode voltage input offset voltage vs temperature supply current vs temperature percent of units - % input offset voltage - v input offset voltage - v temperature - c temperature - c supply curent - a supply voltage - volt 0 10 25 35 10 30 0 40 2 v 2 5 v 3.6v supply current - a typical performance characteristics v rs+ = v rs - = 3.6 v; t a = +25 c, unless otherwise noted. - 40 - 15 10 35 85 60 15 20 0.2 0.6 0 0.4 1 0.8 0 40 - 4 0 20 80 60 0.2 0.6 0.8 0 0.4 1 input offset voltage histogram 5 20 30 50 0 10 15 20 30 25 5 gain error - % 25 20 15 0 10 - 0.2 0.2 - 0.4 0.4 0 gain error histogram percent of units - % 5 30 input offset voltage vs common - mode voltage input offset voltage - v supply voltage - volt 10 15 20 30 25 5 40 35 30 25 20 0 110 - 40 - 15 10 35 85 60 110 - 20
ts1102 ts1102 ds r1p0 page 5 rtfds small - signal gain vs frequency small - signal gain - db 0.001 0.1 1 10 1000 5 - 5 - 15 - 35 - 25 frequency - khz 0 - 10 - 20 - 30 100 typical performance characteristics v rs+ = v rs - = 3.6 v; t a = +25 c, unless otherwise noted. 0.01 gain error vs. temperature gain error - % temperature - c 0 0.1 0.4 0.5 - 0.1 0.2 0.3 gain error vs common - mode voltage supply voltage - volt 0.2 0.3 0.1 gain error - % 0 10 15 20 30 25 5 0 v sense - mv v out vs v sense @ supply = 3.6v 0 150 100 50 0 0.5 2.5 3 3.5 4 1.5 2 v out - v 1 v out - v 0 100 60 20 v sense - mv v out vs v sense @ supply = 2 v 40 80 0.4 1.6 0.8 1.2 0 1.4 1.0 0.6 0.2 common - mode rejection - db common - mode rejection vs frequency 0 - 40 - 80 - 20 - 60 - 100 - 140 - 120 frequency - khz 0.001 0.1 1 10 1000 100 0.01 g = 25 g = 50 g = 100 1.8 2 g = 25 g = 50 g = 100 g = 25 g = 50 g = 100 g = 25 g = 50, 100 - 40 - 15 10 35 85 60 110
ts1102 page 6 ts1102 ds r1p0 rtfds input offset voltage histogram typical performance characteristics v rs+ = v rs - = 3.6 v; t a = +25 c, unless otherwise noted. 200 s/div v sense v out small - signal pulse response, gain = 50 200 s/div large - signal pulse response, gain = 50 v sense v out 200 s/div v sense v out large - signal pulse response, gain = 25 20 0 s/div small - signal pulse response, gain = 25 v sense v out 20 0 s/div small - signal pulse response, gain = 100 v sense v out 200 s/div v sense v out large - signal pulse response, gain = 100
ts1102 ts1102 ds r1p0 page 7 rtfds pin functions pin label function sot23 5 rs+ external sense resistor power - side connection 4 rs - external sense resistor load - side connection 1, 2 gnd ground . connect these pin s to analog ground. 3 out output voltage. v out is proportional to v sense = v rs+ - v rs - block diagram description of operation the internal configuration of the ts1102 C a unidirectional high - side, current - sense amplifier - is based on a commonly - used operational amplifier (op amp) circuit for measuring load currents (in one direction) in the presence of high - common - mode voltages. in the general case, a current - sense am plifier monitors the voltage caused by a load current through an external sense resistor and generates an output voltage as a function of that load current. referring to the typical application circuit on page 1 , the inputs of the op - amp - based circuit are connected across an external rsense resistor that is used to measure load current. at the non - inverting input of the ts1102 (the rs + terminal), the applied voltage is i load x rsense. since the rs - terminal is the non - inverting input of the internal op amp, op - amp feedback action forces the inverting input of the internal op amp to the same potential (i load x rsense). therefore, the voltage drop across rsense (v sense ) and the voltage drop across r gain (at the rs+ terminal) are equal. to minimize any additional error because of op - amp input bias current mismatch, both r gain s are the same value. since the internal p - channel fets source is connected to the inverting input of the internal op amp and since the voltage drop across r gain is the same as the external v sense , op amp feedback action drives the gate of the fet such that the fets drain - sou rce current is equal to: s sese r a
ts1102 page 8 ts1102 ds r1p0 rtfds or s la x r sese r a since the fets drain terminal is connected to r out , the output voltage of the ts1102 at the out terminal is, therefore; t la x r sese x r t r a the current - sense amplifiers gain accuracy is therefore the ratio match of r out to r gain . for each of the four gain options available, table 1 lists the values for r out and r gain . the ts1102 s output stage is protected against input overdrive by use of an output current - limiting circuit of 3ma (typical) and a 7v internal clamp protection circuit . table 1: internal gain setting resistors (typical values) gain (v/v) r gain ( ) r out ( ) part number 25 400 10k ts1102 - 25 50 200 10k ts1102 - 50 100 100 10k ts1102 - 100 200 100 20k ts1102 - 200 to achieve its very - low input offset voltage performance over temperature, vsense voltage, and power supply voltage, the design of the ts1102 s amplifier is chopper - stabilized, a commonly - used technique to reduce significantly the input offset voltage of amplifiers. this method , however, does employ the use of sampling techniques and therefore residue of the ts1102 s 10khz internal clock is contained in the ts1102 s output voltage spectrum. applications informa tion choosing the sense resistor selecting the optimal value for the external rsense is based on the following criteria and for each commentary follows: 1) rsense voltage loss 2) v out swing vs. applied input voltage at v rs+ and desired v sense 3) total i load accuracy 4) circuit efficiency and power dissipation 5) rsense kelvin connections 6) sense resistor composition 1) rsense voltage loss for lowest ir voltage loss in rsense, the smallest usable value for rsense should be selected. 2) v out swing vs. applied input voltage at v rs+ and desired v sense as there is no separate power supply pin for the ts1102 , the circuit draws its power from the applied voltage at both its rs+ and rs - terminal s . therefore, the signal voltage at the out terminal is bounded by the minimum supply voltage applied to the ts1102 . therefore, v out(max) = v rs+(min) - v sense(max) C v oh(max) and r sese t max a la max where the full - scale v sense should be less than v out (max) / a at the applications minimum rs+ terminal voltage. for best performance with a 3.6v power supply, rsense should be chosen to generate a v sense of: a) 120mv (for the 25v/v gain option), b) 60mv (for the 50v/v gain option), c) 30mv (for the 100v/v gain option), or d) 15mv (for the 200v/v gain option) at the full - scale i load (max) current in each application. for the case where the minimum powe r supply voltage is higher than 3.6v, each of the four full - scale v sense s above can be increased. 3) total i l oad accuracy in the ts1102 s linear region where v out < v out( max ) , there are two specifications related to the circuits accuracy: a) the ts1102 s input offset voltage (v os = 2 0 0 , max ) and b) its gain error (ge(max) = 0.5%).
ts1102 ts1102 ds r1p0 page 9 rtfds an expression for the ts1102 s total output voltage (+ error ) is given by: v out = [gain x (1 ge) x v sense ] (gain x v os ) a large value for rsense permits the use of smaller load currents to be measured more accurately because the effects of offset voltages are less significant when compared to larger vsense voltages. due car e though should be exercised as previously mentioned with large values of rsense. 4) circuit efficiency and power dissipation ir losses in rsense can be large especially at high load currents. it is important to select the smallest, usable rsense value to minimize power dissipation and to keep the physical size of rsense small. if the external rsense is allowed to dissipate signi ficant power, then its inherent temperature coefficient may alter its design center value, thereby reducing load current measurement accuracy. precisely because the ts1102 s input stage was designed to exhibit a very low input offset voltage , small rsense values can be used to reduce power dissipation and minimize local hot spots on the pcb. 5) rsense kelvin connections for optimal v sense accuracy in the presence of large load currents, parasitic pcb track resistance should be minimized. kelvin - sense pcb connections between rsense and the ts1102 s rs+ and rs - terminals are strongly recommended. the drawing in figure 1 illustrates the conne ctions between the current - sense amplifier and the current - sense resistor. the pcb layout should be balanced and symmetrical to minimize wiring - induced errors. in addition, the pcb layout for rsense should include good thermal management techniques for opt imal rsense power dissipation. 6 ) rsense composition current - shunt resistors are made available in metal film, metal strip, and wire - wound constructions. wire - wound current - shunt resistors are constructed with wire spirally wound on to a core. as a result , these types of current shunt resistors exhibit the largest self inductance. in applications where the load current contains high - frequency transients, metal film or metal strip current s ense resistors are recommended. internal noise filter in power management and motor control applications, current - sense amplifiers are required to measure load currents accurately in the presence of both externally - generated differential and common - mode noise. an example of differential - mode noise that can ap pear at the inputs of a current - sense amplifier is high - frequency ripple. high - frequency ripple C whether injected into the circuit inductively or capacitively - can produce a differential - mode voltage drop across the external current - shunt resistor (rsens e). an example of externally - generated, common - mode noise is the high - frequency output ripple of a switching regulator that can result in common - mode noise injection into both inputs of a current - sense amplifier. even though the load current signal bandwi dth is dc, the input stage of any current - sense amplifier can rectify unwanted, out - of - band noise that can result in an apparent error voltage at its output. this rectification of noise signals occurs because all amplifier input stages are constructed with transistors that can behave as high - frequency signal detectors in the same way pn - junction diodes were used as rf envelope detectors in early radio designs. against common - mode injected noise, the amplifiers internal common - mode rejection is usually suff icient. to counter the effects of externally - injected noise, it has always been good engineering practice to add external low - pass filters in series with the inputs of a current - sense amplifier. in the design of discrete current - sense amplifiers, resistor s used in the external low - pass filters were incorporated into the circuits overall design so errors because of any input - bias current - generated offset voltage errors and gain errors were compensated. with the advent of monolithic current - sense amplifier s, like the ts1102 , the addition of external figure 1 : making pcb connections to the sense resistor.
ts1102 page 10 ts1102 ds r1p0 rtfds low - pass filters in series with the current - sense amplifiers inputs only introduces additional offset voltage and gain errors. to minimize or eliminate altogether the need for external low - pass filters and to m aintain low input offset voltage and gain errors, the ts1102 incorporates a 50 - khz (typ), 2 nd - order differential low - pass filter as shown in the ts1102 s block diagram. optional output filter capacitor if the ts1102 is part of a signal acquisition system where its out terminal is connected to the input of an adc with an internal, switched - capacitor track - and - hold circuit, the internal track - and - holds sampling capacitor can cause voltage droop at v out . a 22nf to 100nf good - quality ceramic capacitor from the out terminal to gnd forms a low - pass filters with the ts1102 s r out and should be used to minimize voltage droop (holding v out constant during the sample interval. using a capacitor on the out terminal will also redu ce the ts1102 s small - signal bandwidth as well as band - limiting amplifier noise. pc board layout and power - supply bypassing for optimal circuit performance, the ts1102 should be in very close proximity to the external current - sense resistor and the pcb t racks from rsense to the rs+ and the rs - input terminals of the ts1102 should be short and symmetric. also recommended are a ground plane and surface mount resistors and capacitors . using the ts1102 in bidirectional load current applications in many battery - powered systems, it is oftentimes necessary to monitor a batterys discharge and charge currents. to perform this function, a bidirectional current - sense amplifier is re quired. the circuit illustrated in figure 2 shows how two ts1102 s can be configured as a bidirectional current - sense amplifier. as shown in the figure, the rs+/rs - input pair of ts1102 #2 is wired opposite in polarity with respect to the rs+/rs - connections of ts1102 #1. current - sense amplifier #1 therefore measures the discharge current and current - sense amplifier #2 measures the charge current. note that both output voltages are measu red with respect to gnd. when the discharge current is being measured, v out1 is active and v out2 is zero; for the case where charge current is being measured, v out1 is zero, and v out2 is active. figure 2 : using two ts1102 s for bidirectional load current detection
ts1102 touchstone semiconductor, inc. page 11 630 alder drive, milpitas, ca 95035 ts1102 ds r1p0 +1 (408) 215 - 1220 ? www.touchstonesemi.com rtfds package outline draw ing 5 - pin s ot23 package outline drawing (n.b., drawings are not to scale) information furnished by touchstone semiconductor is believed to be accurate and reliable. however, touchstone semiconductor does not assume any responsibility for its use nor for any infringements of patents or other rights of third parties that may result from its use , and all information provided by touchstone semiconductor and its suppliers is provided on an as is basis, without warranty of any kin d . touchstone semiconductor reserves the right to change product spec ifications and product descriptions at any time without any advance notice. no license is granted by implication or otherwise under any patent or patent rights of touchstone semiconductor. touchstone semiconductor assumes no liability for applications assi stance or customer product design. customers are responsible for their products and applications using touchstone semiconductor components. to minimize the risk associated with customer products and applicatio ns, customers should provide adequate design an d operating safeguards. trademarks and registered trademarks are the property of their respective owners. n o t e s : 1 . d i m e n s i o n s a n d t o l e r a n c e s a r e a s p e r a n s i y 1 4 . 5 m , 1 9 8 2 . 2 . p a c k a g e s u r f a c e t o b e m a t t e f i n i s h v d i 1 1 ~ 1 3 . 3 . d i e i s f a c i n g u p m o l d a n d f a c i n g d o w n f o r t r i m / f o r m , i e , r e v e r s e t r i m / f o r m . 4 . t h e f o o t l e n g t h m e a s u r i n g i s b a s e d o n t h e g a u g e p l a n e m e t h o d . 5 . d i m e n s i o n s a r e e x c l u s i v e o f m o l d f l a s h a n d g a t e b u r r . 6 . d i m e n s i o n s a r e e x c l u s i v e o f s o l d e r p l a t i n g . 7 . a l l d i m e n s i o n s a r e i n m m . 8 . t h i s p a r t i s c o m p l i a n t w i t h e i a j s p e c . a n d j e d e c m o - 1 7 8 a a 9 . l e a d s p a n / s t a n d o f f h e i g h t / c o p l a n a r i t y a r e c o n s i d e r e d a s s p e c i a l c h a r a c t e r i s t i c . 5 . 2 . 8 0 - 3 . 0 0 2 . 6 0 - 3 . 0 0 1 . 5 0 - 1 . 7 5 0 . 9 5 0 . 9 5 0 t y p 5 5 0 . 3 0 - 0 . 5 0 0 . 0 0 - 0 . 1 5 1 0 o t y p 1 0 o t y p 1 0 o t y p 0 . 0 9 - 0 . 2 0 5 1 0 o t y p 0 o - 8 o 0 . 3 0 - 0 . 5 5 0 . 2 5 g a u g e p l a n e 1 . 9 0 m a x 0 . 1 0 m a x 0 . 0 9 C 1 . 4 5 0 . 5 0 C 0 . 7 0 1 . 5 0 C 1 . 7 5 0 . 5 0 m a x 0 . 3 0 m i n 0 . 2 0 m a x 0 . 0 9 m i n 0 . 9 0 - 1 . 3 0 0 . 6 0 C 0 . 8 0 t y p

▲Up To Search▲

Price & Availability of TS1102-25EG5T

	To Download TS1102-25EG5T Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .